• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    The invention relates to a converter for transmitting electrical energy between an AC voltage system at mains input terminals (a, b, c) and a DC voltage system at DC voltage terminals (p, n), which has: intermediate nodes (x, y, z), in particular the same number of intermediate terminals how network input terminals (a, b, c) exist; a phase selection network (5) for selectively connecting each of the network input terminals (a, b, c) to each of the intermediate nodes (x, y, z); a primary-side inverter bridge (6) for selectively connecting each of the intermediate nodes (x, y, z) to one of two primary-side connections (g, h); an inductive network for electrically isolated energy transmission between the two primary connections (g, h) and two secondary connections (j, k); a secondary rectifier bridge (3) for selectively connecting each of the two secondary terminals (j, k) to each of the DC terminals (p, n).
    公开号:CH715318A2
    申请号:CH01085/18
    申请日:2018-09-13
    公开日:2020-03-13
    发明作者:Franz Josef Schrittwieser Lukas；Walter Kolar Johann
    申请人:Eth Zuerich；
    IPC主号:
    专利说明:

    According to the prior art, DC voltage consumers with a connected load of ten kilowatts, or more, are supplied from a three-phase AC network. Active pulse rectifier circuits are used which enable the output voltage to be regulated and generate approximately sinusoidal mains currents in order to minimize mains interference.
    If the output DC voltage to be generated is substantially higher or lower than the rectification value of the three-phase AC supply voltage, a floating DC converter, which includes a transformer, is usually connected downstream of the pulse rectifier stage. Electrical isolation between the AC voltage and DC voltage side may also be necessary for safety reasons or due to different earthing schemes on the AC and DC voltage side. A possible implementation of such a two-stage, electrically isolated rectifier is shown in FIG. 1. The pulse rectifier stage 1 consists of three input inductors La, Lb, Lc and a three-phase bridge consisting of six semiconductor switches that can be switched off. The DC voltage connection of the three-phase bridge is connected to an intermediate circuit capacitor CZK, whereby an approximately constant intermediate circuit voltage UZK is generated by means of a suitable control of the three-phase bridge. An inverter full bridge 2 consisting of four semiconductor switches that can be switched off is connected to this intermediate circuit voltage. The series connection of an inductor L1 and the primary winding of a transformer T1 of the DC-DC converter is connected between the outputs of the full inverter bridge 2. A rectifier full bridge 3, also consisting of four semiconductor switches that can be switched off, is connected to the secondary winding of the transformer T1, the positive and the negative connection of the full bridge representing the positive output p and the negative output n (also called output terminals or DC voltage terminals) of the rectifier. An output capacitor Cdc is typically connected between the nodes p and n, which receives the switching frequency current components of the full rectifier bridge and stabilizes the output DC voltage.
    An alternative circuit which allows a single-stage energy conversion between the three-phase AC voltage and the DC voltage is shown in Fig. 2. In comparison to FIG. 1, the pulse rectifier stage, the intermediate circuit capacitor and the full inverter bridge are replaced by a direct matrix converter 4, which consists of six bidirectionally lockable and conductive switches. Three of these switches are each connected to one of the input terminals a, b and c (also called mains input terminals or AC voltage terminals) of the three-phase AC voltage and to a connection of the inductance U, the other three bidirectional switches are also connected to the input terminals a, b and c, as well as connected to a connection of the primary-side transformer winding. Each bidirectional switch is implemented by an antiserial circuit of two bipolar conductive and unipolar lockable semiconductor switches. Typically three filter capacitors Q are connected to the input terminals a, b and c of the three-phase AC voltage in order to achieve continuous and approximately sinusoidal mains phase currents ia, iband ic.
    Compared with the circuit in Fig. 1 results in a lower implementation effort in terms of size, losses and / or costs because the intermediate circuit capacitor CZK and the input inductors La, Lbund Lcentfallen and the additional two semiconductor switches and three filter capacitors C usually required smaller size, losses and / or Show more costs than the components that are no longer required. An otherwise typically required precharge circuit for the intermediate circuit capacitor CZK can also be omitted since the filter capacitors C usually have a significantly smaller capacitance than the intermediate circuit capacitor CZK. However, this results in a more complex control circuit for the switches, since the commutation of the bidirectional switches must take place in four steps with blocking times in between in order to offer the current ip impressed by the inductance L1 a valid routing path at all times and to ensure that none of the external conductor voltages between the terminals a, b and c is short-circuited. In general, four different commutation sequences are required, since a corresponding commutation sequence must be selected depending on the sign of the current ip and the sign of the desired change in the output voltage of the matrix converter.
    [0005] A possible object of the invention is to provide an alternative to conventional circuits. Another possible object of the invention is to reduce the implementation effort or the complexity of the control circuit, with the same functionality and without using additional passive components. Another possible object of the invention is the implementation of a system for wireless energy transmission between a three-phase AC voltage and a DC voltage, with low network perturbations being achieved on the AC voltage side.
    The object is achieved by a converter according to the claims.
    A corresponding converter for the electrically isolated transmission of electrical energy between an AC (AC) system at mains input terminals (a, b, c) and a DC (DC) system at DC terminals (p, n) has:Intermediate nodes (x, y, z), in particular the same number of intermediate terminals (x, y, z) as network input terminals (a, b, c);a phase selection network (5) for selectively connecting each of the network input terminals (a, b, c) to each of the intermediate nodes (x, y, z);a primary-side inverter bridge (6) for selectively connecting each of the intermediate nodes (x, y, z) to one of two primary-side connections (g, h);an inductive network for electrically isolated energy transmission between the two primary connections (g, h) and two secondary connections (j, k);a secondary rectifier bridge (3) for selectively connecting each of the two secondary terminals (j, k) to each of the DC terminals (p, n).
    Further embodiments emerge from the dependent claims.
    Brief description of the figures
    The object of the invention is explained below with reference to preferred embodiments, illustrated in the accompanying drawings. It shows schematically:<tb> Fig. 1 <SEP> Potential-isolated, two-stage, three-phase rectifier circuit with low network perturbations according to the prior art, with a pulse rectifier 1, an intermediate circuit capacitor CZK, an inverter bridge 2, an inductor L1, a transformer T1; a full rectifier bridge 3 and an output capacitor Cdc.<tb> Fig. 2 <SEP> Isolated, single-stage, three-phase rectifier circuit with low network perturbations according to the prior art, with three input filter capacitors Cf, a direct matrix converter 4 with three inputs and two outputs, an inductor L1, a transformer T1, an active full rectifier bridge 3 and an output capacitor Cdc .<tb> Fig. 3 <SEP> Isolated, single-stage, three-phase rectifier circuit with low network perturbations according to the invention, with a phase selection bridge 5, which is formed by a three-phase six-pulse diode bridge and three bipolar blocking and conductive switches, the input filter capacitors Cf, a primary-side three-point inverter full bridge 6, formed by eight bipolar conductive switchable semiconductor switches (hereinafter also referred to as inverter switches), an inductor L1, a transformer T1, a secondary full rectifier bridge 3 formed by four bipolar conductive switchable semiconductors, and an output capacitor Cdc.<tb> Fig. 4 <SEP> Possible alternative implementations of the three-point full inverter bridge: The circuit shown in FIG. 4a requires four additional diodes in comparison to FIG. 3, but this results in a lower voltage stress on all semiconductors. The implementation shown in FIG. 4b requires only six bipolar conductive, switchable semiconductor switches, but an additional eight diodes.<tb> Fig. 5 <SEP> Typical curves of the primary-side inverter voltage up and the secondary-side rectifier input voltage us, during a pulse period for the case uxy≥ uyz. The control signals of the eight inverter switches Sxg, Sgy, Syg, Sgz, Sxh, Shy, Syhund Shz, and the control signals of the four switches Spj, Sjn, Spkund Sknder active rectifier bridge are also shown.<tb> Fig. 6 <SEP> Typical curves of the primary-side inverter voltage up during a pulse period for the case uxy≥ uyz. The eight control signals of the inverter switches Sxg, Sgy, Syg, Sgz, Sxh, Shy, Syhund Shz are shown.<tb> Fig. 7 <SEP> Classification of a time profile of the three-phase mains voltages, among others, ub and ucin twelve sectors s which are given by the potential order and the sign of the phase voltages.Also shown are the resulting potentials ux, uy and uz at nodes x, y and z (also called intermediate nodes) of the circuit according to FIG. 3, and the resulting voltages uxy and uyz (also called upper and lower intermediate voltages) between the corresponding nodes. The last line indicates in which sectors the modulation schemes according to FIG. 5 or according to FIG. 6 are used.<tb> Fig. 8 <SEP> Possible alternative implementations of the electrically isolated, inductive network between the primary and secondary side with different combinations of series and parallel elements on the primary and secondary side.<tb> Fig. 9 <SEP> Possible implementation of regulation of the rectifier circuit according to the invention, the DC output voltage being regulated up-and-over by a regulator Gug. The translation of the measured line phase and output voltages and a required output current setpoint idc <*> into the four switching times t1, t2, t3 and t4 is carried out using a conversion table (lookup table, LUT in FIG. 9). These switching times and the sector s in which the line voltage space pointer is currently located are then fed to a pulse width modulator (PWM in FIG. 9), which generates the switching signals of the semiconductors according to FIGS. 5 and 6.<tb> Fig. 10 <SEP> circuit according to the invention for wireless energy transmission between a three-phase AC voltage and a DC voltage, with a phase selection bridge 5, a three-point inverter full bridge 6, an inductive, wireless energy transmission system 7 formed by two coupled coils L1 and L2, each of which has a capacitor C1 and C2 Compensation of the reactive power that occurs is connected in series, as well as a secondary full rectifier bridge 3 and an output capacitor Cdc.<tb> Fig. 11 <SEP> Typical curves of the primary-side inverter voltage up, the secondary-side rectifier voltage us and the resulting primary-side coil current ip during a pulse period, for a wireless energy transmission system according to FIG. 10.
    Ways of Carrying Out the Invention
    With the invention, it is possible to feed DC voltage consumers by means of a single-stage energy conversion from the three-phase AC network, a potential separation between the AC and DC voltage side, and approximately sinusoidal network phase currents and thus low network perturbations can be achieved. In contrast to the prior art, all active switches can be controlled directly by means of pulse width modulation, without commutation sequences with several steps. A corresponding circuit is shown in FIG. 3, with a phase selection network 5, in this case a phase selection bridge, three filter capacitors Cf, a three-point full inverter bridge 6, an inductive network, for example having an inductance L1 and a transformer T1, an active full rectifier bridge 3, and an output capacitor Cdc. The phase selection network 5, the three filter capacitors Cf, and the three-point inverter full bridge 6 are connected to one another at three nodes x, y, z (also called intermediate nodes). The phase selection network 5 has a three-phase six-pulse diode bridge, which is connected to the network input terminals a, b and c and whose positive output is connected to the node x of the circuit and whose negative output is connected to the node z of the circuits. In addition, a bipolar blocking and conductive switch Saya, Sbybund Scycan is connected to each of the three network input terminals a, b and c, the remaining connections of these switches being connected to node y of the circuit. As described in EP 3 113 345, that switch Saya, Sbyboder Scyce is switched on whose two associated diodes of the three-phase six-pulse diode bridge do not conduct. As a result, the power input terminal with the highest potential is connected to node x, the power input terminal with the lowest potential is connected to node z and the remaining power input terminal is connected to node y. A circuit which enables the reversal of the power flow direction from the DC to the AC voltage side can be implemented by supplementing or replacing the three-phase six-pulse diode bridge with six additional semiconductor switches which can be switched off, as described in EP 3 113 345.
    At the nodes x, y and z of the circuit, three filter capacitors Cf are connected which can either form a common star point or can be connected in a delta connection with the nodes x, y and z. The three-point full inverter bridge 6, consisting of two half bridges, is also connected to nodes x, y and z and forms the primary-side inverter voltage up between nodes g and h (primary-side connections of the electrically isolated inductive network). The first half bridge consists of a bipolar conductive switch Sxg, which is connected between the nodes x and g, two anti-series connected switches Sygund Sgy, which are connected to the nodes y and g, and a bipolar conductive switch Sgz, which is connected between the nodes g and z is switched. The second half bridge consists of a bipolar conductive switch Sxh, which is connected between the nodes x and h, two anti-series switches Syhund Shy, which are connected to the nodes y and h, and a bipolar conductive switch Shz, which is connected between the nodes h and z is switched. Connected to nodes g and h is the electrically isolated inductive network, in this case the series connection of inductance L1 and the primary winding of transformer T1, in which the current flows ip. The secondary winding of the transformer T1 is connected to the nodes j and k (connections on the secondary side of the electrically isolated inductive network) of the circuit, which are connected to the active full rectifier bridge 3. This consists of two half bridges, each with two bipolar conductive switches. The first half-bridge consists of an upper switch Spj, which is connected to the positive output terminal p and node j, and a lower switch Sjn, which is connected to node j and the negative output terminal n. The second half bridge consists of an upper switch Spk, which is connected to the output terminal p and the node k, and a lower switch Skn, which is connected to the node k and the output terminal n. An output capacitor Cdc can also be connected between the output terminals p and n, which stabilizes the DC output voltage.
    Alternative implementation options for the full inverter bridge 6 are shown in FIG. 4. 4a consists of two identical half bridges, the first half bridge consisting of an upper series connection of two bipolar conductive switches between nodes x and g, and a lower series connection of two bipolar conductive switches between nodes g and z. The connection points of the two series connections are each connected to node y via a diode, the upper diode being oriented such that it enables current to flow from node y to the connection point of the upper series connection, and the lower diode is oriented such that it allows current to flow from Connection point of the lower series connection to node y enables. The second half-bridge also consists of an upper series connection of two bipolar conductive switches between nodes x and h, and a lower series connection of two bipolar conductive switches between nodes h and z. The connection points of the two series connections of the second half bridge are each connected to node y via a diode, the upper diode being oriented such that it allows current to flow from node y to the connection point of the upper series connection and the lower diode is oriented such that it enables current to flow from the connection point of the lower series connection to node y. Compared to the full inverter bridge shown in FIG. 3, four additional diodes are required, but the reverse voltage stress of all semiconductors is reduced, or the circuit can be operated at a higher input AC voltage with given semiconductor switches.
    Another possible implementation of the three-point inverter full bridge 6 is shown in Fig. 4b, which also consists of two identical half bridges. The first half bridge consists of an upper bipolar conductive switch which is connected between the nodes x and g, a lower bipolar conductive switch which is connected between the nodes g and z, and a bipolar conductive and blocking network which is connected between the nodes y and g is connected and consists of a full-bridge rectifier, formed by four diodes, and an at least unipolar conductive and lockable switch. The positive and negative connections of the full-bridge rectifier are connected to the switch, and the two remaining connections of the full-bridge rectifier are connected to nodes y and g. The second half-bridge consists of an upper bipolar conductive switch which is connected between nodes x and h, a lower bipolar conductive switch which is connected between nodes h and z, and a bipolar conductive and blocking network which is connected between nodes y and h is switched and consists of a full-bridge rectifier, formed by four diodes, and an at least unipolar conductive and lockable switch. The positive and negative connections of the full-bridge rectifier are connected to the switch, and the two remaining connections of the full-bridge rectifier are connected to nodes y and h.
    Typical curves of the primary-side inverter voltage up and the secondary-side rectifier voltage us, as well as the resulting primary-side transformer current ips are shown schematically in FIG. 5 for a pulse period Tp, the curve shape of up only being valid for the case uxy≥ uyz. Before the pulse period begins, at least switches Sxg and Sxhe are switched on. At the beginning of the pulse period at t = 0, the three-point inverter half-bridge, which is connected to node h, connects it to node z by switching the switches Sxhund Syhaus and at least switching on the switch Shze, whereby the switch Shy can also be switched on. This results in the inverter voltage up = uxz at the output of the full inverter bridge 6. At time t = Tp / 2 - t2, the switch Shz is switched off and Syhund Shye is switched on, as a result of which the node h is connected to the node y and the inverter voltage up = uxyresults. At the time Tp / 2 - t1, at least the switch Shy, and optionally also the switch Syh, are switched off and the switch Sxhe is switched on. This connects node h to node x and results in an inverter voltage up = 0. In the middle of the pulse period at t = Tp / 2 the switches Sxg and Syg are switched off and at least the switch Sgz, optionally also the switch Sgy, is switched on the node g is connected to the node z and an inverter voltage up = -uxz results. At time t = Tp - t2, switch Sgz is turned off and switches Syg and Sgye are turned on, connecting node g to node y and resulting in an inverter voltage up = -uxy. At time t = Tp - t1, the switch Sgy, and optionally also the switch Syg, are switched off and the switch Sxge is switched on, as a result of which the node g is connected to the node x and the inverter voltage up = 0 results. Each time after the previously conductive switches have been switched off and before the switches which are subsequently switched on are switched on, a locking time must typically be waited to avoid short circuits between nodes x, y and z and the resulting high current peaks.
    As in dual active bridge converters according to the prior art, the secondary rectifier full bridge 3 generates a mean value-free square wave voltage, shown schematically in FIG. 5, with a variable pulse width and a variable phase shift with respect to the beginning of the pulse period. The amplitude of the square-wave voltage is defined by the output voltage between the terminals p and n. As shown, the two switches Spj and Spktypisch with two compared to the beginning of the pulse period by t3 or. t4 phase-shifted square-wave signals controlled with a pulse width of 50%. The switch Sjn is switched on when Spj is switched off and vice versa, typically a lock time is observed during the switching process in which both switches are switched off in order to avoid short-circuiting of the nodes p and n. In the same way, the switch Skne is switched on when the switch Spk is switched off and a locking time is again observed.
    The curve shape of up for the case uxy≤ uyz is shown schematically in FIG. 6. Before the start of the pulse period, at least switches Sgz and Shze are switched on, as a result of which nodes g and h are both connected to node z. At the beginning of the pulse period at t = 0, the switch Sgz, and possibly the switch Sgy, is switched off and the switch Sxg, and optionally also the switch Syge, is switched on. This connects node g to node x and results in the inverter voltage up = uxz. At time t = Tp / 2 - t2 the switch Sxg is switched off and the switches Sgy and Syge are switched on, whereby the node g is connected to the node y and the inverter voltage results up = uyz. At time t = Tp / 2 - t1, the switch Syg, and optionally also the switch Sgy, is switched off and the switch Sgze is switched on. This connects node g to node z and results in an inverter voltage up = 0. At the middle of the pulse period at t = Tp / 2, switch Shz and possibly also switch Shy are switched off and switch Sxh, and optionally also switch Syh switch, on. This connects node h to node x and results in the inverter voltage up = -uxz. At time t = Tp - t2 the switch Sx is switched on and the switches Shy and Syhe are switched on, whereby the node h is connected to the node y and the inverter voltage results up = -uyz. At time Tp-t1, the switch Syhund, optionally also the switch Shy, is switched off and the switch Shze is switched on, whereby the node h is connected to the node z and the inverter voltage up = 0 results. As stated above, a locking time is typically waited between the switch-off and switch-on processes in order to avoid short circuits between nodes x, y and z.
    In order to minimize mains interference of the rectifier and the formation of reactive power in the three-phase AC network, the four parameters t1 to t4 are chosen so that the mains voltages, among other things, ub and ucproportional input currents ia, ibund i result, the amplitude of the currents or that taken from the network Active power, typically specified by a superimposed output voltage control. Essentially, the power drawn is influenced by the phase shift between up and us and the minimization of reactive power is achieved by setting the ratio of t1 and t2. Since only two of the four available degrees of freedom are required, the four parameters can be determined in such a way that the effective values of the currents ip and isin the primary and secondary transformer windings are minimized, which minimizes the conduction losses in the windings and in the switches.
    The division of the three-phase AC voltage into twelve sectors s is shown in Fig. 7, each sector being defined by different signs and potential order of the three phase voltages, among others, ub and uc. The following applies in sector 1: among others> 0> ub≥ uc, in sector 2: among others> ub≥ 0> uc, in sector 3: ub≥ among others> 0> uc and so on. Also shown are the voltages ux, uy and uz between the nodes x, y and z and the star point of the three-phase AC network, and the resulting voltages uxy and uyz between the corresponding nodes. As shown in the last line, the switching sequence shown in FIG. 5 is used in sectors 1, 4, 5, 8, 9 and 12 and that according to FIG. 6 in the remaining sectors 2, 3, 6, 7, 10 and 11 .
    Alternative implementation options of the electrically isolated, inductive network between nodes g and h and j and k are shown in FIG. 8. In general, these networks consist of a transformer T1 and a combination of one or more series elements, designated L1 and L2, which record the difference between the primary-side inverter voltage up and the secondary-side rectifier voltage us. In addition, one or two parallel elements, designated Lm1 and Lm2, can be inserted in order to achieve de-energized switching of the full inverter bridge 6 and the full rectifier bridge 3.
    In Fig. 8a, a first inductor L1 is connected in series with the primary winding of the transformer T1 and a second inductor L2 is connected in series with the secondary winding of the transformer T1. In Fig. 8b a first inductor L1 is connected in series with the primary winding of the transformer T1 and a second inductor Lm1 is connected in parallel with this series connection.
    In Fig. 8c a first inductor L1 is connected in series with the primary winding of the transformer T1 and a second inductor Lm2is connected in parallel with the secondary winding of the transformer T1.
    In Fig. 8d, a first inductor L1 is connected in series with the primary winding of the transformer T1, a second inductor Lm1 is connected in parallel with this series connection and a third inductor Lm2 is connected in parallel with the secondary winding of the transformer T1.
    In Fig. 8e, a first inductor L2 is connected in series with the secondary winding of the transformer T1.
    In Fig. 8f a first inductor L2 is connected in series with the secondary winding of the transformer T1 and a second inductor Lm1 is connected in parallel with the primary winding of the transformer T1.
    In Fig. 8g, a first inductor L2 is connected in series with the secondary winding of the transformer T1 and a second inductor Lm2 is connected in parallel with this series connection.
    In Fig. 8h a first inductor L2 is connected in series with the secondary winding of the transformer T1, a second inductor Lm2 is connected in parallel with this series connection and a third inductor Lm1 is connected in parallel with the primary winding of the transformer T1.
    In Fig. 8i, the primary-side inverter voltage up between terminals g and h is applied directly to the primary winding of transformer T1 and the secondary-side rectifier voltage us between terminals j and k is applied directly to the secondary winding of the transformer. As in the case of dual active bridge converters according to the prior art, in this case the transformer must be designed with a sufficiently large magnetic leakage flux to replace the functionality of the omitted series inductance and to limit the amplitude of the currents ip and is.
    A possible implementation of the regulation of the isolated rectifier according to the invention is shown in FIG. 9. The sector s in which the space pointer of the mains voltage is located is determined from the measured string voltages, among other things, ub and uc, according to the scheme shown in FIG. 7. The corresponding bipolar conductive and lockable switch Saya, Sbyb or Scyce is switched on by means of a table A. The measured DC output voltage upn is compared with its assigned reference value upn <*> and the error signal is fed to a controller Gu. The manipulated variable g <*> of this controller corresponds to the conductance of an equivalent, symmetrical three-phase consumer that can be achieved on the AC voltage side. By multiplying by the buzzer of the squares of the measured string voltages and then dividing by the measured DC output voltage, the setpoint of the DC voltage output current idc <*> results. This, together with the phase voltages, the sector s and the measured DC output voltage is used to determine the relative switching times t1, t2, t3 and t4 of the modulation method shown in FIGS. 5 and 6 by means of a conversion table (LUT in FIG. 9). The four switching times t1, t2, t3 and t4 are fed to a pulse width modulator (PWM in FIG. 9) which supplies the required control signals of the switches Sxg, Syg, Sgy, Sgz, Sxh; Syh, Shy, Shz, Spj, Sjn, Spkund Skner.
    A possible implementation of a single-stage, wireless energy transmission system with low network perturbations according to the invention, which is fed by a three-phase AC voltage at terminals a, b and c and provides a DC output voltage at terminals p and n, is shown in FIG. 10 shown. Compared to the electrically isolated rectifier circuit shown in Fig. 3, the inductive network between the primary and secondary sides is replaced by two magnetically coupled and mechanically separated coils L1 and L2. Due to the significantly lower magnetic coupling compared to a conventional transformer, capacitors are typically used to compensate for the resulting reactive power, the example of series compensation with capacitors C1 and C2 being shown in FIG. 10. Typical curves of the primary-side inverter voltage up, the secondary-side rectifier voltage, and the resulting coil current ips are shown in FIG. 11. Due to the reactive power compensation by C1 and C2, an approximately sinusoidal current ip results in the coils.
    权利要求:
    Claims (10)
    [1]
    1. A converter for the electrically isolated transmission of electrical energy between an alternating voltage (AC) system on mains input terminals (a, b, c) and a direct voltage (DC) system on direct voltage terminals (p, n)- Intermediate nodes (x, y, z), with in particular the same number of intermediate terminals (x, y, z) as network input terminals (a, b, c);- a phase selection network (5) for selectively connecting each of the network input terminals (a, b, c) to each of the intermediate nodes (x, y, z);- A primary-side inverter bridge (6) for selectively connecting each of the intermediate nodes (x, y, z) with one of two primary-side connections (g, h);- an inductive network for electrically isolated energy transmission between the two primary connections (g, h) and two secondary connections (j, k);- A secondary-side rectifier bridge (3) for the optional connection of each of the two secondary-side connections (j, k) with each of the DC voltage terminals (p, n).
    [2]
    2. Converter according to claim 1, wherein the phase selection network (5) is set up to in each case the network input terminal with the highest potential with the first intermediate node (x), the network input terminal with the lowest potential with the third intermediate node (z) and the remaining network input terminal with to connect the second intermediate node (y).
    [3]
    3. Converter according to claim 1 or 2, wherein the phase selection network (5) between the network input terminals (a, b, c), a first intermediate node (x) and a third intermediate node (z) has a three-phase six-pulse diode bridge, and between each the network input terminals (a, b, c) and a second intermediate node (y) each have a bipolar lockable and bipolar conductive switch.
    [4]
    4. Converter according to one of the preceding claims, wherein the primary-side inverter bridge (6) is a three-point inverter full bridge.
    [5]
    5. Converter according to one of claims 1 to 3, wherein the primary-side inverter bridge (6) a first half bridge with a first upper series connection of two bipolar conductive switches between the first intermediate node (x) and a first primary-side connection (g), and with a first lower series connection of two bipolar conductive switches between the first primary-side connection (g) and the third intermediate node (z),wherein connection points of the first two series connections are each connected to the second intermediate node (y) via a first lower or upper diode, the first upper diode being oriented such that it enables a current to flow from the second intermediate node (y) to the connection point of the upper series connection and the first lower diode is oriented in such a way that it enables a current to flow from the connection point of the lower series circuit to the second intermediate node (y),and the primary-side inverter bridge (6)a second half bridge with a second upper series connection of two bipolar conductive switches between the first intermediate node (x) and a second primary-side connection (h), and with a second lower series connection of two bipolar conductive switches between the second primary-side connection (h) and the third intermediate node (z),wherein connection points of the two second series connections are each connected to the second intermediate node (y) via a second lower or upper diode, the second upper diode being oriented such that it enables a current to flow from the second intermediate node (y) to the connection point of the upper series connection and the second lower diode is oriented in such a way that it enables current to flow from the connection point of the lower series circuit to the second intermediate node (y).
    [6]
    6. Converter according to one of claims 1 to 3, wherein the primary-side inverter bridge (6) has:a first half bridge with a first upper bipolar conductive switch which is connected between the first intermediate node (x) and a first primary-side connection (g), a first lower bipolar conductive switch which is connected between the first primary-side connection (g) and the third intermediate node ( z) is switched,a first bipolar conductive and lockable network, which is connected between the second intermediate node (y) and the first primary-side connection (g),a second half bridge with a second upper bipolar conductive switch which is connected between the first intermediate node (x) and a second primary-side connection (h), a second lower bipolar conductive switch which is connected between the second primary-side connection (h) and the third intermediate node ( z) is switched,a second bipolar conductive and lockable network, which is connected between the second intermediate node (y) and the second primary-side connector (h).
    [7]
    7. Converter according to claim 6, wherein the first and / or the second bipolar conductive and lockable network each have a full bridge rectifier, formed from four diodes, and an at least unipolar conductive and lockable switch, the positive and the negative connection of the full bridge rectifier are connected via this switch and the two remaining connections of the full-bridge rectifier are connected to the second intermediate node (y) and the first primary-side connection (g) and the second primary-side connection (h), respectively.
    [8]
    8. Converter according to one of the preceding claims, wherein the inductive network for electrically isolated energy transmission has a transformer, optionally connected in series and / or parallel to windings of this transformer, inductors and / or compensation capacitors.
    [9]
    9. Converter according to one of the preceding claims, wherein the secondary-side rectifier bridge (3) is an active full rectifier bridge.
    [10]
    10. Converter according to one of the preceding claims, comprising a regulation which is set up to carry out the following method:- Determining, based on measured string voltages, among other things, ub and ucder network input terminals (a, b, c), a sector (s) in which the space pointer of the network voltage is located;- Determining a bipolar conductive and lockable switch (Saya, Sbyboder Scyc) of the phase selection network (5) assigned to this sector (s), and switching this switch on;- Comparing a measured DC output voltage (upn) with an assigned reference value (upn <*>) and feeding its difference to a controller (Gu) as an error signal;- Determining, by means of this controller (Gu), a manipulated variable (g <*>) corresponding to a conductance value to be achieved on the AC voltage side of an equivalent, symmetrical three-phase consumer;- Determining a target value of a DC output current (idc <*>) by multiplying the manipulated variable by the buzzer of the squares of the measured phase voltages and then dividing by the measured DC output voltage (upn);- Determination of relative switching times (t1, t2, t3, t4) of a modulation method based on the setpoint of the DC-side output current (idc <*>), the phase voltages, the sector (s) and the measured DC output voltage (upn);- Generating control signals from switches (Sxg, Syg, Sgy, Sgz, Sxh, Syh, Shy, Shz) of the primary-side inverter bridge (6) and switches (Spj, Sjn, Spk, Skn) of the secondary-side rectifier bridge (3) using a pulse width modulator the switching times (t1, t2, t3 and t4).
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    同族专利:
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    CH715318B1|2021-10-29|
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
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    CH01085/18A|CH715318B1|2018-09-13|2018-09-13|Isolated AC-DC converter.|CH01085/18A| CH715318B1|2018-09-13|2018-09-13|Isolated AC-DC converter.|
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